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KA7526
Power Factor Correction Controller
Features
* Internal Startup Timer * Internal R/C filter which eliminates the Need for an External R/C filter * Overvoltage Comparator eliminates Runaway Output Voltage * Zero Current Detector * One Quadrant Multiplier * Trimmed 1.5% Internal Bandgap Reference * Under Voltage Lock Out with 5V of Hysteresis * Totem Pole Output with High State Clamp * Low Startup and Operating Current * 8-Pin DIP or 8-Pin SOP
Descriptions
The KA7526 provides simple and high performance active power factor correction. KA7526 is optimized for electronic ballast and low power, high density power supplies requiring a minimum board area, reduced component count and low power dissipation. Addition of internal R/C filter eliminates the need for an external R/C filter. Internal clamping of the error amplifier and multiplier outputs improves turn on overshoot characteristics and current limiting. Special circuitry has also been added to prevent no load runaway conditions. The output drive clamping circuit limits overshoot of the power MOSFET gate drive Independent of supply voltage, so that it greatly enhance the system reliability.
Applications
* Electronic Ballast * SMPS
8-DIP
1 8-SOP
1
Rev. 5.0
(c)2000 Fairchild Semiconductor International
KA7526
Internal Block Diagram
VCC
8
2.5V Ref 5V
+
VCC Internal Bias
36V 13V
-
UVLO
7 OUT
Drive Output Timer R
Idet
5
7.5V 1.8V 40k
+ -
240mV
S
Q
Zero Current Detector
-
Over Voltage Protection R
+ -
CS
4
8pF
+
Current Sense Comparator Vref
1.8V
1.65V
Vmo
Vm1 MULT
Multiplier
+
Vm2 Vref~Vref+2V
+ -
Vref Vea(-) Error Amp
3
0~3.8V
1
INV
Pin4 Threshold(Vmo) K= Vm1 (Vm2-Vref)
GND
6
2
EA OUT
IC Characteristics
Parmaeter UVLO Multiplier Input Range (Vm1) Multiplier Input Range (Vm2) Maximum Current Sense Voltage KA7526 8/13V 0 ~ 3.8V Vref ~ Verf + 2V 1.65V
2
KA7526
PIN Assignments
INV
1
8
Vcc
EA OUT
2
7
OUT
MULT
3
6
GND
CS
4
5
Idet
(Top View)
Pin Definitions
Pin Number 1 2 3 Pin Name INV EA OUT MULT Pin Function Descrition Inverting input of the error amplifier. The output of the boost converter should be resistively divided to 2.5V and connected to this pin. The output of the error amplifier. A feedback compensation network is placed between this pin and the INV pin Input to the multiplier stage. The full-wave rectified AC is divided to less than 3.8V and is connected to this pin. Input to the PWM comparator. The Current is sensed in the boost stage by a resistor in the source lead of MOSFET. An internal leading edge blanking circuitry has been included to reject any high frequency noise present on the current waveform. The zero current detector senses the inductor current by monitoring when the boost inductor auxilary winding voltage falls below 1.8V. The ground potential of all the pins. The output of a high-current power driver capable of driving the gate of a power MOSFET. The logic and control power supply connection.
4
CS
5 6 7 8
Idet GND OUT VCC
3
KA7526
Absolute Maximum Ratings
Parameter Supply voltage Peak drive output current Driver output clamping diodes VO>VCC or VO<-0.3V Detector clamping diodes Error amp, multiplier and comparator input voltage Operating temperature range Storage temperature range Power dissipation
(Note) (Note)
Symbol VCC IOH, IOI Iclamp Idet VIN Topr Tstg Pd qja
Value 30 500 10 3 -0.3 to 6 -25 to 125 -65 to 150 0.8 100
Unit V mA mA mA V
oC o
C
W
o
Thermal resistance (Junction-to-air)
Note : Based in 8-DIP
C/W
Temperature Characteristics (-25oC Ta 125oC )
Parameter Temperature stability for reference voltage(Vref) Temperature stability for multiplier gain(K) Symbol Vref (Typ) K/T (Typ) Value 20 -0.2 Unit mV %/oC
4
KA7526
Electrical Characteristics
Unless otherwise specified, for typical values Vcc=12V, Ta=25oC, for Min/Max values Ta is the operating ambient temperature range with -25oC Ta 125oC. Parameter UNDER VOLTAGE LOCK OUT SECTION Start Threshold Voltage UVLO Hysteresis Supply Zener Voltage SUPPLY CURRENT SECTION Start Up Supply Current Operating Supply Current Dynamic Operating Supply Current ERROR AMPLIFIER SECTION Voltage Feedback Input Threshold Line Regulation Load Regulation
(Note1)
Symbol Vth (st) HY(st) Vz Ist ICC Idcc
Condition VCC Increasing ICC=10mA VCCMin. 12 4 30 -
Typ. 13 5 36 0.3 4 5
Max. 14 6 0.4 8 10
Unit V V V mA mA mA
Vref Vref1 Vref2 Vref3 Ib(ea) Isource Isink
2.44 -0.5 -2 3 1.2 -0.5 0 Vref 0.49 1.55 -
0.1 0.1 20 -4.5 4.5 0.6 0.62 1.65 -0.2
2.56 10 10 0.5 5.6 0.5 3.8 Vref+2 0.74 1.75 -
V mV mV mV A mA mA V V/s A V V 1/V V %/oC
Temperature Stability of Vref (Note2) Input Bias Current Output Source Current Output Sink Current Output Voltage Range Slew Rate MULTIPLIER SECTION Input Bias Current (pin3) M1 Input Voltage Range (pin3) M2 Input Voltage Range (pin2) Multiplier Gain (Note3) Maximum Multiplier Output Voltage Temperature Stability of K
(Note2) (Note2)
Veao SR Ib(m) Vm1 Vm2 K Vomax(m) K/T
5
KA7526
Electrical Characteristics (Continued)
Parameter CURRENT SENSE SECTION Input Offset Voltage (Note2) Input Bias Current Current Sense Delay to Output (Note2) DETECT SECTION Detect Input Threshold Detect Hysteresis Input Low Clamp Voltage Input High Clamp Voltage Input Bias Current Input High/low Clamp Diode Current OUTPUT DRIVER SECTION Output Voltage High Output Voltage Low Rising Time (Note2) Falling Time
(Note2) (Note2)
Symbol Vio(cs) Ib(cs) td(cs) Vth(det) HY(det) Vclamp(I) Vclamp(h) Ib(det) Iclamp VOH VOL tr tf Vomax(o) Vomin(o) td(rst)
Condition Vm1=0V, Vm2=2.2V 0VVCC1.7V Vdet Increasing Idet=-100A Idet=3mA 1VVdet6V IO=-10mA, VCC=12V IO=10mA, VCC=12V CI=1nF CI=1nF VCC=20V VCC=5V, IO=100A Vm1=1V, Vm2=3.5V Vcs=-0.5V, Vm1=1V Vdet=0V
Min. -10 -1 1.5 180 0.45 6.7 -1 8.5 12 -
Typ. 3 -0.3 200 1.8 240 0.75 7.5 -0.2 9 0.8 130 50 13 300
Max. Unit 10 1 500 2.1 400 1 8.3 1 3 1 200 120 15 1 mV A ns V mV V V A mA V V ns ns V V s
Maximum Output Voltage Output Voltage With Uvlo Activated RESTART TIMER SECTION Restart Time Delay OVERVOLTAGE PROTECTION SECTION Voltage Feedback Input Threshold
Vth(ovp)
1.7
1.8
1.9
V
Notes : 1. Because the reference is not brought out externally, this specification cannot be tested on the package part. It is guaranteed by design. 2. This parameter, although guaranteed, is not tested in production. 3. K =
Pin4 Threshold Vm1x(Vm2-Vref)
(Vm1=Vpin3, Vm2=Vpin2)
6
KA7526
Typical Performance Characteristics
Fig1. E.A. Output Voltage vs C.S. Threshold
1.8 1.6
Vm1=4V
Fig2. Multiplier Input Voltage vs C.S. Threshold
1.8 1.6
Veao=5V
1.4 1.2
Vm1=1V
1.4
C.S. Threshold Voltage [V]
C.S Threshold Voltage [V]
Vm1=1.5V
Veao=3.25V
1.2 1.0
Veao=3V
1.0 0.8 0.6
Vm1=0.5V
0.8 0.6 0.4 0.2
Veao=2.5V Veao=2.75V
0.4 0.2 0.0 -0.2 2.5 3.0 3.5 4.0 4.5 5.0 EA Output Voltage [V]
0.0 -0.2 0 1 2 3 4 5 Multiplier Input Voltage [V]
Figure 1. EA Output Voltage vs C.S. Threshold
Fig3. Supply Current VS Supply Voltage
20.0 17.5 15.0 12.5 10.0 7.5 5.0 2.5 0.0 0 5 10 15 20 25 30 35 40 45 Supply Voltage [v]
Figure 2. Multiplier Input Voltage vs C.S. Threshold
Fig4. Reference Voltage vs Temperature
2.54 2.53 2.52
Reference Voltage(V)
2.51 2.50 2.49 2.48 2.47 2.46 2.45 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
Supply Current [mA]
Figure 3. Supply Current vs Supply Voltage
Fig5. Start-up Threshold vs Temperature
13.4 13.3
Figure 4. Reference Voltage vs Temperature
Fig6. UV Lockout Hysteresis vs Temperature
6.5
6.0
Start-Up Threshold Voltage(V)
13.2 UV Lockout Hysteresis(V) 13.1 13.0 12.9 12.8 12.7
4.0 5.5
5.0
4.5
12.6 12.5 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
3.5 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature ()
Figure 5. Start-Up Threshold vs Temperature
Figure 6. UV Lockout Hysteresis vs Temperature
7
KA7526
Typical Performance Characteristics (continued)
Fig7. Start-up Supply Current vs Temperature
0.40 0.36 0.32
Fig8. E.A. Source Current vs Temperature
-2 -3 -4
Start-up Supply Current(mA)
EA Source Current(mA)
0.28 0.24 0.20 0.16 0.12 0.08
-5 -6 -7 -8 -9
0.04 0.00 -40 -10 -20 0 20 40 60 80 100 120 140 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature() Ambient Temperature()
Figure 7. Start-Up Supply Current vs Temperature
Fig9. Sink Current vs Temperature
10 9 8 7
Figure 8. EA Source Current vs Temperature
Fig.10 Input Bias Current vs Temperature
0.5 0.4 0.3
EA Input Bias Current( )
-40 -20 0 20 40 60 80 100 120 140
0.2 0.1 0.0 -0.1 -0.2 -0.3 -0.4 -0.5 -40 -20 0 20 40 60 80 100 120 140
EA Sink Current(mA)
6 5 4 3 2 1 0 Ambient Temperature()
Ambient Temperature()
Figure 9. EA Sink Current vs Temperature
Fig.11 Multiplier Gain vs Temperature
0.75
Figure 10. EA Input Bias Current vs Temperature
Fig.12 Idet Threshold High vs Temperature
1.92 0.70 1.88
Multiplier Gain(1/V)
0.65
Idet Threshold High(V)
-40 -20 0 20 40 60 80 100 120 140
1.84 1.80 1.76 1.72
0.60
0.55
0.50 1.68 0.45 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature() Ambient Temperature()
Figure 11. Multiplier Gain vs Temperature
Figure 12. Idet Threshold Volyage vs Temperature
8
KA7526
Typical Performance Characteristics (continued)
Fig.13 Idet Input Hysteresis vs Temperature
400 360
Fig.14 Restart Time vs Temperature
600
500
320 280 240 200 160 120 80 40 0 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
Idet Input Hysteresis(mV)
400
Restart Time( )
300
200
100
0 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
Figure 13. Idet Input Hysteresis vs Temperature
Fig.15 Max. Mult. Output Voltage vs Temperature
1.85 1.80 1.75
Figure 14. Restart Time vs Temperature
Fig.16 Supply Current vs Temperature
8 7 6
Max. Multi Output Voltage(V)
1.70 1.65 1.60 1.55 1.50 1.45 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
Supply Current(mA)
5 4 3 2 1 0 -40 -20 0 20 40 60 80 100 120 140 Ambient Temperature()
Figure 15. Max.Mult.Output Voltage vs Temperature
Figure 16. Supply Current vs Temperature
9
KA7526
Operating Description
KA7526 is high performance, critical conduction, current-mode power factor controller specifically designed for use in offline active preconverters with minimal external components. This device provides the necessary features which are required to significantly en-hance poor power factor loads by keeping the ac line current sinusoidal and in phase with the line voltage. KA7526 contains many of the building blocks and protection features that are employed in modern high performance current mode power supply controllers. A description of each of the function blocks is given below.
START-UP
An Undervoltage Lockout comparator has been incorporated to guarantee that IC is fully functional before enabling the output stage. The positive power supply terminal (Vcc) is monitored by the UVLO comparator with the upper threshold set at 13V and the lower threshold at 8V. In the stand-by mode, with Vcc at 12.5V, the required supply current is less than 0.3mA . This large hysteresis and low start-up current allow the implementation of efficient bootstrap start-up techniques, making this device ideally suited for wide range off-line preconverter applications. Fig.1.1 shows the start-up circuit. Circuit operation is as follows: The start-up capacitor (Cst) is charged by current through start-up resistor (Rst) minus the start-up current drawn by the IC. Once the capacitor voltage reaches the start-up threshold, the IC turns on, starting the switching of the MOSFET. The operation of the IC demands an increase in operating current which results in discharging the capacitor. Before the start-up capacitor voltage is discharged below hysteresis voltage, the auxiliary winding voltage takes over as the supply voltage as shown in Fig. 1.2.
Rst DVcc AC input + Cst Vcc Out
KA7526
Fig.1.1 Start-up Circuit
Vcc Cst discharges Vstart Hysteresis
Cst charges from Rst
t
Fig.1.2 Start-up Capacitor Voltage
10
KA7526
Error Amplifier
An Error Amplifier with access to the inverting input and output is provided. The noninverting input is internally biased at 2.5V and is not pinned out. The output voltage of the power factor converter is typically divided down and monitored by the inverting input. The error amp output is internally connected to the multiplier and is pinned out for external loop compensation. Typically, the loopbandwidth is set below 20Hz, so that the amplifer's output voltage is relatively constant over a given ac line cycle. In effect, the error amp monitors the average output voltage of the converter over several line cycles. Input bias current(0.5uA, max) can cause an output voltage error that is equal to the product of the input bias current and the value of the upper divider resistor, R1 in Fig. 2.1.
1.8V Over Voltage To Drive Comparator Output Shutdown + R1 + R2 1 INV Vref
Vref
+
_ +x To Multiplier
R3
-
2 Ccomp EA OUT Band width= 1/(2xR1xCcomp)
Fig.2.1 Error Amp and Over Voltage Comparator
Over Voltage Protection
The low bandwidth (typically below 20Hz) characteristic of Error Amplifier control loop results in output voltage runaway condition. This condition can occur during initial start-up, sudden load removal, or during output arcing. The over voltage comparator monitors the output voltage of the error amplifier. When load is removed, error amp output swings lower than 1.8V, comparator is triggered high and output driver is turned off till the error amp inverting input voltage drops below 2.5V. At this point, the error amp output swings positive, turns the output driver back on. .
Multiplier
A single quadrant, two input multiplier is the critical element that enables this device to get power factor correction. One input of multiplier(Pin 3) is connected to an external resistor divider which monitors the rectified ac line. The other input is internally driven by a DC voltage which is the difference of error amplifier output (Pin 2) and reference voltage, Vref. The multiplier is designed to have an extremely linear transfer curve over a wide dynamic range, 0V to 3.8V for Pin 3, and 2.5V to 4.5V for error amplifier output under all line and load conditions. The multiplier output controls the current sense comparator threshold as the ac voltage traverses sinusoidally from zero to peak line. This allows the inductor peak current to follow the ac line thus forcing the average input current to be sinusoidal. In other words, this has the effect of forcing the MOSFET on-time to track the input line voltage, resulting in a fixed drive output on-time, thus making the preconverter load appear to be resistive to the ac line. The equation below describes the relationship between multiplier output and inputs. Vmo = K x Vm1 x (Vm2-Vref) K : Multiplier gain Vm1: Voltage at Pin 3 Vm2: Error amp output voltage Vmo: Multiplier output voltage
11
KA7526
Current Sense Comparator + 1.65V
CS 4
+
Vref Vmo Error Amp. - Vm2 + ++ 2 EA OUT
3 MULT
Vm1
1 INV
Fig.3.1 Multiplier Block
Current Sense Comparator
The current sense comparator adopt the RS latch configuration to ensure that only a single pulse appears at the drive output during a given cycle. MOSFET drain current is converted to voltage using an external sense resistor in series with the external power MOSFET. When sense voltage exceeds the threshold set by the multiplier output, the current sense comparator terminates the gate drive to the MOSFET and resets the PWM latch. The latch insures that the output remains in a low state after the MOSFET drain current falls back to zero. The peak inductor current under normal operating conditions is controlled by the multiplier output, Vmo. Abnormal operating conditions occur during preconverter start-up at extremely high line or as output voltage sensing is lost. Under these conditions, the multiplier output and current sense threshold will be internally clamped to 1.65V. Therefore, the maximum peak switch current is limited to: Ipk(max) = 1.65V / Rsense An internal R/C filter has been included to attenuate any high frequency noise that may be present on the current waveform. This circuit block eliminates the need for an external R/C filter otherwise required for proper operation of the circuit.
cs
+ 1.65V Multiplier Output
4 Rsense External R/C Filter can be eliminated
Fig. 4.1 Current Sense Circuit
12
KA7526
Zero Current Detector
KA7526 operates as a critical conduction current mode controller. The power MOSFET is turned on by the zero current detector and turned off when the peak inductor current reaches the threshold level established by the multiplier output. The slope of the inductor current is indirectly detected by monitoring the voltage across a separate winding and connecting it to the zero current detector Pin 5. Once the inductor current reaches ground level, the voltage across the winding reverses polarity. When the Idet input falls below 1.8V, the comparator output is triggered to the low state. To prevent false tripping, 240mV of hysteresis is provided. The zero current detector input is internally protected by two clamps. The upper 7.5V clamp prevents input over voltage breakdown while the lower 0.75V clamp prevents substrate injection. An internal current limit resistor protects the lower clamp transistor in case the Idet pin is accidently shorted to ground. A watchdog timer function was added to the IC to eliminate the need for an external oscillator when used in stand-alone applications. The timer provides a means to automatically start or restart the preconverter if the drive output has been off for more than 300us after the inductor current reaches zero.
Drive Output
The KA7526 contains a single totem-pole output stage specifically designed for direct drive of power MOSFET. The drive output is capable of up to 500mA peak current with a typical rise and fall time of 130ns, 50ns each with a 1.0nF load. Additional internal circuitry has been added to keep the drive output in a sinking mode whenever the UVLO is active. This characteristic eliminates the need for an external gate pull-down resistor. Internal voltage clamping ensures that output driver is always lower than 13V when supply voltage variation exceeds more than rated Vgs threshold (typ 20V) of the external MOSFET. This eliminates an external zener diode and extra power dissipation associated with it that otherwise is required for reliable circuit operation.
13
KA7526
APPLICATION CIRCUIT #1
< 90 ~ 265VAC Input, 400VDC, 32Wx2 Lamps Self-oscillating Ballast >
L2 D5 L6 C4 R1 D4 D3 R4 D6 R2 D2 R7 R5 D7 5 8 C2 C1 3 L1 C7 V1 Fuse R3 + C5 R8 R11 Q3 R15 C12 AC Input GND L5 C16 6 4 L7 R16 C13 C3 7 2 + C14 C6 1 C8 C10 D8 Q1 R9 C9 R6 R10 Q2 R13 C11 L5 L5 R18 L3 L4 R14 R17
D1
Lamp 1
C15
Lamp 2
KA7526 IC 1
14
KA7526
Component Listing (for Application circuit #1)
Reference R1, 2 R3 R4 R5 R6, 13, 15 R7 R8 R9 R10 R11 R12, 17, 18 R14, 16 C1 C2, 3 C4 C5 C6 C7 C8 C9 C10 C11, 12 C13 C14, 15 C16 D1, 2, 3, 4, 7 D5 D6 D8 L1 L2 L3, 4 L5 L6, 7 Fuse V1 IC1 Q1 Q2, 3 Value 1.2M-F, 1/4W 11k-F, 1/4W 150k , 1/2W 22k-J, 1/4W 47-J, 1/4W 3.3, 1/4W 1-J, 1W 180k-F, 1/4W 820k-F, 1/4W 6.8k-F, 1/4W 390k-J, 1/4W 8.2-J, 1/4W 0.15uF, 630V 2200pF, 3000V 0.22uF, 630V 22uF, 35V 0.33uF, 25V 1000pF, 50V 47uF, 450V 4700pF, 630V 2200pF, 630V 0.15uF, 63V 0.1uF, 50V 8200pF, 1000V 0.15uF, 630V 1000V, 1A 1000V, 1.5A 75V, 150mA DR 10x12 EI 2519 EI 2820 SB5S 8x3x4 10uH 430V 500V, 4.5A 400V, 5A Part Number 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type MEP-CAP Y-CAP MPE-CAP Electrolytic Ceramic Ceramic Electrolytic PPF-CAP PPF-CAP MPF-CAP Ceramic PP-CAP MEP-CAP IN4007GP BYV26C IN4148 N413N (DIAC) DIT-010 DBT-002 DPT-086 DDT-005 BS24-100K 52NM250V, 3A INR140, 431 KA7526 QFP6N50 KSC5305D Manufacturer Philips FairChild FairChild FairChild
15
KA7526
Application Circuit #2
< 90 ~ 265VAC Input, 400VDC, 32Wx2 Lamps External-oscillating Ballast >
Full-wave Rectified Output L2 Fuse C1 V1 L1 C2 C4 + D2 D4 C6 R4 C3 C5 R5 R7 NTC D6 D1 D3 R3 R6 Q1 C9 R9 + D5 R8 PFC Output
AC Input
8
7
6
5
R1 1 C8
KA7526
2 C7 3 4
R2
To PFC Output R10 T1 + C9 R11 Q3 C14 L4 D7 R16 To Full-wave Rectified Output R12 + C10 Z1 1 C11 C12 2 3 4 R13 C13 R17 8 7 6 D8 Q2 R14 L3 C15 Lamp1 Lamp2
R15 C19 C17
R16 C18
C20
5
KA7541
R18 R19
16
KA7526
Component Listing (for Application Circuit #2)
Reference R1 R2 R3, 12 R4 R5, 10, 11 R6 R7 R8 R9 R13 R14 R15, 16 R17, 18 R19 C1, 2 C3, 4 C5 C6 C7 C8 C9 C10 C11 C12 C13 C14 C15, 16 C17, 18, 19, 20 D1, 2, 3, 4 D5 D6 D7,8 L1 L2 L3, 4 T1 Fuse V1 Q1, 2, 3 Z1 Value 2.2M-F, 1/4W 12k-F, 1/4W 150k , 1/2W 22k-J, 1/4W 47-J, 1/4W 3.3, 1/4W 1-J, 1W 1.2M-F, 1/4W 10k Variable Resistor 22k-F, 1/4W 180k-J, 1/4W 330k-J, 1/4W 680k-J, 1/4W 8.2k-J, 1/4W 0.15uF, 630V 2200pF, 3000V 0.1uF, 400V 22uF, 35V 0.33uF, 25V 0.01uF, 25V 47uF, 450V 47uF, 35V 0.22uF, 25V 180pF, 25V 0.1uF, 25V 1000pF, 630V 4700pF, 1000V 6800pF, 630V 1000V, 1A FRD(25nS) 75V, 150mA 1000V, 1.5A 80mH 1.2mH (100T: 7T) Litz Wire or USTC 3.1mH Litz Wire or USTC 1.2mH(35T:24T:24T) 430V 500V, 6A 15V, 1W Part Number 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type 26mm Type MEP-CAP Y-CAP MPE-CAP Electrolytic MPE-CAP MPE-CAP Electrolytic Electrolytic MPE-CAP Ceramic MPE-CAP MPE-CAP MPE-CAP MPE-CAP 1N4007 BYV26C 1N4148 1N4937 BSF2125 EI2820 EI2820 EE1614 52NM250V, 3A INR140, 431 SKP6N50 Manufacturer Philips FairChild 17
KA7526
Mechanical Dimensions
Package Dimensions in millimeters
8-DIP
1.524 0.10 0.018 0.004 0.060 0.004 0.46 0.10 6.40 0.20 0.252 0.008 ( #1 #8 9.20 0.20 0.362 0.008 9.60 MAX 0.378 #4 #5 2.54 0.100 5.08 MAX 0.200 7.62 0.300 3.40 0.20 0.134 0.008 3.30 0.30 0.130 0.012 0.33 0.013 MIN 0.79 ) 0.031
0.25 -0.05
0~15
+0.10
0.010 -0.002
+0.004
18
KA7526
Mechanical Dimensions (Continued)
Package Dimensions in millimeters
8-SOP
MIN 1.55 0.20 0.061 0.008 0.1~0.25 0.004~0.001
#1
#8 4.92 0.20 0.194 0.008 5.13 MAX 0.202
( #4 #5 6.00 0.30 0.236 0.012
+0.10 0.15 -0.05 +0.004 0.006 -0.002
0.56 ) 0.022 1.80 MAX 0.071 MAX0.10 MAX0.004 3.95 0.20 0.156 0.008 5.72 0.225 0.50 0.20 0.020 0.008
0~
8
1.27 0.050
0.41 0.10 0.016 0.004
19
KA7526
Ordering Information
Product Number KA7526 KA7526D Package 8-DIP 8-SOP Operating Temperature -25 ~ +125oC
20
KA7526
21
KA7526
DISCLAIMER FAIRCHILD SEMICONDUCTOR RESERVES THE RIGHT TO MAKE CHANGES WITHOUT FURTHER NOTICE TO ANY PRODUCTS HEREIN TO IMPROVE RELIABILITY, FUNCTION OR DESIGN. FAIRCHILD DOES NOT ASSUME ANY LIABILITY ARISING OUT OF THE APPLICATION OR USE OF ANY PRODUCT OR CIRCUIT DESCRIBED HEREIN; NEITHER DOES IT CONVEY ANY LICENSE UNDER ITS PATENT RIGHTS, NOR THE RIGHTS OF OTHERS. LIFE SUPPORT POLICY FAIRCHILD'S PRODUCTS ARE NOT AUTHORIZED FOR USE AS CRITICAL COMPONENTS IN LIFE SUPPORT DEVICES OR SYSTEMS WITHOUT THE EXPRESS WRITTEN APPROVAL OF THE PRESIDENT OF FAIRCHILD SEMICONDUCTOR INTERNATIONAL. As used herein: 1. Life support devices or systems are devices or systems which, (a) are intended for surgical implant into the body, or (b) support or sustain life, and (c) whose failure to perform when properly used in accordance with instructions for use provided in the labeling, can be reasonably expected to result in a significant injury of the user.
www.fairchildsemi.com 9/25/00 0.0m 001 Stock#DSxxxxxxxx 2000 Fairchild Semiconductor International
2. A critical component in any component of a life support device or system whose failure to perform can be reasonably expected to cause the failure of the life support device or system, or to affect its safety or effectiveness.

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